By Luca Corradini, Dragan Maksimović, Paolo Mattavelli, Regan Zane
This publication is targeted at the basic points of study, modeling and layout of electronic keep watch over loops round high-frequency switched-mode strength converters in a scientific and rigorous manner
- Comprehensive remedy of electronic regulate concept for energy converters
- Verilog and VHDL pattern codes are provided
- Enables readers to effectively examine, version, layout, and enforce voltage, present, or multi-loop electronic suggestions loops round switched-mode strength converters
- Practical examples are used during the ebook to demonstrate purposes of the recommendations developed
- Matlab examples also are provided
Read Online or Download Digital Control of High-Frequency Switched-Mode Power Converters PDF
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Extra info for Digital Control of High-Frequency Switched-Mode Power Converters
In the diagram, Gc (s) represents the compensator transfer function to be designed. From the block diagram, the system loop gain T (s) can be defined by opening the feedback loop as suggested in Fig. 9 Small-signal block diagram of the analog voltage-mode control. 10 vˆ ¯o (t) Gvd (s) GPWM (s) u ˆy (s) u ˆx (s) Definition of the system loop gain T (s). function between u ˆx and u ˆy , T (s) − u ˆy (s) u ˆx (s) = Gc (s)GPWM (s)Gvd (s)H(s) . 24) vˆref =0 The uncompensated loop gain Tu (s), on the other hand, is defined as the system loop gain when a unity compensation is employed, that is, when Gc (s) = 1, Tu (s) GPWM (s)Gvd (s)H(s) .
One exception to this occurs when x(t) has a triangular switching ripple, in which case the approximation is justified even in the presence of a large ripple component. 2. 8 (a) Buck converter and its (b) averaged and (c) small-signal models. ˆ (t) = x(t) − X denotes the small-signal component of x(t) with respect to where x the dc component X. 8(c) illustrates the averaged, small-signal equivalent circuit of the Buck converter obtained after the linearization process. 21) L . C The converter small-signal behavior is therefore that of a second-order system with resonant frequency and Q-factor (ω0 , Q), and with a real left half-plane (LHP) zero located at s = −ωESR .
It can be shown that the steady-state analysis proceeds as stated earlier for the small-ripple approximation. In practice, the linear-ripple approximation is easier to meet, especially when considering inductor current waveforms. As long as the small-ripple approximation is satisfied for capacitor voltages, in fact, inductor currents retain triangular waveforms even when the peak-to-peak ripple is not negligibly small compared with the dc component. It is worth mentioning, at this point, that the above discussion is implicitly focused on the converters operating in continuous conduction mode (CCM), where the use of the small-ripple or linear-ripple approximation is well justified for all the converter state variables.
Digital Control of High-Frequency Switched-Mode Power Converters by Luca Corradini, Dragan Maksimović, Paolo Mattavelli, Regan Zane